Method for reducing interference from scattered light/reflected light of interference path by generating carrier through phase

ABSTRACT

A method for reducing interference from scattered light/reflected light of an interference path by generating carrier through phase. Phase modulation is applied on the terminal of a fiber path, and a target signal is separated from an interference signal by selecting a specific working point, to obtain a purer target signal, thereby lengthening the measurement distance. The signal demodulation manner used in this method is different from the traditional manner of modulation performed by generating a carrier through the phase, and does not need to use the modulation frequency as the reference signal during demodulation, so this manner is easily implemented. The method is applicable to long-distance pipeline monitoring and wide-range fiber perimeter security, and especially to an application environment in which the modulation end is far away from the signal demodulation end. The method can also be applied in an application in which measurement is implemented by modulating an optical transmission phase in a feedback device.

TECHNICAL FIELD

The present invention belongs to the field of optical fiber sensing technology, in particular eliminate the impact of backscattered light in an optical fiber sensor.

BACKGROUND

Optical fiber sensing technology is often used in large-scale, long-distance monitoring, such as security monitoring used in oil pipelines, high-voltage power grids, pipelines, communications cable and other infrastructure, which the fiber used to be the sensor, real-timely acquiring related disturbance signal, determine the location of the disturbance occurred by the analysis characterize. The structure of single core feedback optical path is: using a single fiber as sensing fiber, the fiber itself is not closed, only apply a feedback device at the end of the fiber, such as a mirror constituting interference optical path. In practice, this structure laying is flexible. The characteristics of such monitoring systems is: light carrying the disturbance information transmitted to the end of the fiber, then reflect by feedback device.

The following is a positioning technology of single core feedback positioning system.

As shown in FIG. 1, we use a sensing section for the optical fiber (optical cable). 1 is the start point of the optical fiber (optical cable), and 2 is a feedback device at the end of the sensing section, such as a mirror. The incident light retrace through the feedback device. Suppose there is a disturbance at point D outside, modulation of light phase is φ(t), when the light twice perturbed points D, phase modulation is subject to:

φ₁(t)=φ(t)+φ(t−T)

wherein, T=2n_(eff)L/c, L is the distance between disturbance point D and feedback device 2, c is the speed of light in vacuum, n _(eff) is the effective refractive index of the optical fiber.

As shown in FIG. 2, we configure an interference optical path.

Interference optical path include the following parts: N * M (N, M are integers) coupler 3, P * Q (P, Q are integers) coupler 4, optical fiber delayer 5 (delay τ), an optical fiber (optical cable) 6, and feedback device 2. 3 a 1, 3 a 2, . . . , 3 aN, 3 b 1, 3 b 2 are ports of coupler 3, 3 a 1, 3 a 2, , 3 aN are co-rotating ports with a total of N, 3 b 1, 3 b 2 are two ports in another group co-rotating ports (with a total of M) of coupler 3. 4 a 1, 4 a 2, 4 b 1 are ports of coupler 4, 4 a 1, 4 a 2 are two ports in a group co-rotating ports (with a total of P) of coupler 4, 4 b 1 are two ports in another group co-rotating ports (with a total of Q) of coupler 4. Optical fiber 6 is induction optical fiber. Feedback device 2 make the light transmitted along the fiber go back to the fiber 6 and return to the coupler 4. Light source input through the port 3 a 1 of coupler 3, after splitting in coupler 3, output respectively through the port 3 b 1, 3 b 2, two optical paths is:

: 3 b 1→5→4 a 1→4 b 1→6→2→6→4→b 1→4 a 2→3 b 2

II: 3 b 2→4 a 2→4 b 1→6→2→6→4 b 1→4 a 1→5→3 b 1

The two optical paths join at coupler 3 again and generate interference, interference signals output respectively through port 3 a 1, 3 a 2, . . . , 3 aN.

In the interference optical path, the light firstly enter delayer 5 and then enter fiber cable 6, the phase modulation applied to the light is:

φ₂(t)=φ(t−τ)+(t−τ−T)

Phase difference between two coherent interference lights is:

Δφ=[φ(t)+φ(t−T)]−[φ(t−τ)+φ(t−τ−T)]

In the spectrum of phase difference, there is a frequency drop point, or “notch point”, and we can determine the location of the disturbance arising according to the notch point. “Notch point” is shown in FIG. 3, in this amplitude—frequency diagram obtained by time frequency transform, the “O” mark the notch point. The relationship between notch point and disturbance position is:

${{f_{null}(k)} = {\frac{k}{2} \cdot \frac{c}{2n_{eff}L}}},\left( {{k = {{2n} - 1}},{n \in N}} \right.$

wherein, f _(null) (k) is frequency of k-order notch point.

We can see from the above principle, the coherent light must transmit from the endpoint 1 of sensing optical fiber 6 to endpoint 2 and then return to sensing optical fiber 6, in order to carry the position “L” message. However, in practice, due to the structural characteristics of the optical fiber and the fiber itself defects and other reasons, there is a scattered light in optical fibers, such as Rayleigh scattering light and the like.

As shown in FIG. 4, 7 is a scatter point, backscattered light along the optical cable go back to interference structure, and therefore there is two beams:

I: 3 b 1→5→4 a 1→4 b 1→6→7→6→4 b 1→4 a 2→3 b 2

II: 3 b 2→4 a 2→4 b 1→6→7→6→4 b 1→4 a 1→5→3 b 1

Because of similar spectral characteristics, the optical path are equal without disturbance, and therefore join at the coupler 3 again will also occur interference. Obviously, the information carried by the two beam of interference light is the length L₇ between point 7 and disturbance point D. 8 is another scattering point, the length information carried by the interference formed by backscatter is the length L₈ between point 8 and disturbance point D, apparently, L₇≠L₈≠L, since these interference is mixed at the output, the interference light generated by Brillouin backscattered light or Raman backscattered light can be filter out by optical filter, but for the interference light generated by Rayleigh scattering light, or the interference light generated by contact point of optical path, it is impossible to eliminate by optical filtering method, will affect the purity of useful interference signal, and will directly affect the accuracy of the disturbance L position. Generally, the intensity of interference generated by backscattered light, contact reflected is significantly less than the intensity of interference generated by reflected light (effective interference signal), and will not have a significant impact on the effective interference signal, accuracy of L can meet the actual needs. But after the monitoring circuit reach a certain length, scattered light affects the entire line obviously, then we can observe the obvious interference signal distortion has occurred, the system can not obtain a valid interference signal normally.

Similarly, reflection by the contact point of optical path can also cause the same adverse effects on the interference signal.

The impact of scatter (reflect) light in the conventional path is not only the obvious restriction in monitoring system. When a large scatter (reflect) point exists, the system can not be properly tested in the line.

In order to cut the impact of the signal, the invention 201010508357.2 (FIG. 5) is proposed by use phase generated carrier technology to separate effective interference phase information from optical output mixed with backscattered light, contact point reflected light interference signal to obtain pure signal having effective disturbance position information, so as to eliminate the impact of back scattered light and the like purposes. In the technology, at the end of sensing optical fiber (optical cable) 6, access a phase modulator 9 close to the feedback device 2, apply modulation signal to phase modulator 9 to obtain carrier fundamental frequency (or double frequency) sideband signal only contains useful information is extracted, and the use of PGC demodulation side information extracted. PGC demodulation techniques generally use coherent demodulation technique in which demodulation process requires the use of homologous signal modulation signal as a reference signal. Due to the need to obtain a modulated signal at signal generation side, in the application of single feedback system, when the end with a signal modulation (position of 9) away from the signal generation side, how to obtain a reference signal, the method becomes difficulty to achieve.

SUMMARY OF THE INVENTION

The purpose of the present invention is to provide a method to eliminate the impact of backscattered light in optical fiber sensor.

The present invention provides a method, use phase modulation technique to separate the target signal from the interfering signals formed by scattering/reflecting in optical fiber path by a simple high-pass filtering, to obtain pure signal having effective disturbance position signal. The setting of phase-modulated signal's amplitude make sidebands of 0 frequency do not contain a valid form of components, only contains interference signal by backscatter, but the fundamental and harmonic frequency modulation sidebands do not include interference signal. On this basis, using a high-pass filter can eliminate the disturbing signal of stray light. Compared with the traditional PGC demodulation, demodulation without using phase modulation signal applied at the signal as a reference signal homologous, structure of this method is simple and easier to implement. Specific methods are as follows.

Connection in optical path is shown in FIG. 5. To be able to distinguish between the two interference signals, the analysis of selecting the modulation signal operating point is as follows.

Phase modulator introduce the interferometer phase difference ΔΦ_(c)(t), after reaching feedback means 2 through the phase modulator, the light reflect to the optical cable and occurs interference signal, the signal is expressed as:

P=p ₁cos[Φ₀+ΔΦ₁(t)+ΔΦ_(c)(t)]  (1)

wherein, p₁ is a constant coefficient related to the system parameters, Φ₀ is an initial phase of the interference structures and a constant, ΔΦ₁(t) is an interference phase difference caused by disturbance;

As to the back scattered light caused by previous path in the phase modulator 9 in optical fable, do not through phase modulator as shown in FIG. 5, changes in the phase are not affected by the signal applied to the phase modulator, part of the optical interference signal is expressed as:

$\begin{matrix} {P_{B} = {\sum\limits_{i}{p_{Bi}{\cos\left( {\varphi_{B\; 0\; i} + {\Delta \; {\varphi_{B\; 1i}(t)}}} \right\rbrack}}}} & (2) \end{matrix}$

wherein, p _(Bi) is an interference coefficient caused by the i-th scattering point of the optical fiber, Φ_(B 0 i) is an initial phase corresponding to the i-th scattering point, ΔΦ_(B1i)(t) is an interference phase difference corresponding to the i-th scattering point and caused by disturbance,

$\sum\limits_{i}$

represented the sum of all the scattered points along the previous induction fiber of phase modulator 9.

The total output signal change portion indicates as follows:

P _(alt) =P+P _(B)   (3)

sinusoidal signal applied to the phase modulator 9 have frequency f_(m), sinusoidal carrier signal ΔΦ_(c)(t) generated by the optical path can be expressed as:

ΔΦ_(c)(t)=Φ_(m)cos(2πf _(m) t)   (4)

Φ_(m) is the amplitude of Δ Φ _(c) (t).

J_(n) order Bessel function expansion of Formula (1) is expressed as:

$\begin{matrix} {\begin{matrix} {P = {p_{1}{\cos \left\lbrack {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}} + {\varphi_{m}{\cos \left( {2\pi \; f_{m}t} \right)}}} \right\rbrack}}} \\ {= {{p_{1}{{\cos \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}\left\lbrack {{J_{0}\left( \varphi_{m} \right)} + {2{J_{2}\left( \varphi_{m} \right)}{\cos \left( {4\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack}} +}} \\ {{p_{1}{{\sin \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}\left\lbrack {{2{J_{1}\left( \varphi_{m} \right)}{\cos \left( {2\pi \; f_{m}t} \right)}} + {2{J_{3}\left( \varphi_{m} \right)}{\cos \left( {6\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack}}} \end{matrix}{and}} & (5) \\ \begin{matrix} {P_{alt} = {P + P_{B}}} \\ {= {P_{B} + {p_{1}{{\cos \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}\left\lbrack {{J_{0}\left( {{\varphi_{0}\left( \varphi_{m} \right)} + {2{J_{2}\left( \varphi_{m} \right)}{\cos \left( {4\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack} +} \right.}}}} \\ {{p_{1}{{\sin \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}\left\lbrack {{2{J_{1}\left( \varphi_{m} \right)}{\cos \left( {2\pi \; f_{m}t} \right)}} + {2{J_{3}\left( \varphi_{m} \right)}{\cos \left( {6\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack}}} \\ {= {\left\lbrack {P_{B} + {p_{1}{{\cos \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)} \cdot {J_{0}\left( \varphi_{m} \right)}}}} \right\rbrack +}} \\ {{p_{1}{{\cos \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}\left\lbrack {{2{J_{2}\left( \varphi_{m} \right)}{\cos \left( {4\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack}}} \\ {{p_{1}{{\sin \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}\left\lbrack {{2{J_{1}\left( \varphi_{m} \right)}{\cos \left( {2\pi \; f_{m}t} \right)}} + {2{J_{3}\left( \varphi_{m} \right)}{\cos \left( {6\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack}}} \end{matrix} & (6) \end{matrix}$

Adjusting the amplitude of the sinusoidal signal, so that:

J ₀(Φ_(m))=0   (7)

P _(alt) =P+ _(B) =P _(B) +p ₁cos(Φ₀+ΔΦ₁(t))[2J ₂(Φ_(m))cos(4πf _(m) t)+ . . . ]+p ₁sin(Φ₀+ΔΦ₁(t))[2J ₁(Φ_(m))cos(2πf _(m) t)+2J ₃(Φ_(m))cos(6πf _(m) t)+ . . . ]  (8)

At this time,

$\begin{matrix} \begin{matrix} {P = {0 + {p_{1}{{\cos \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}\left\lbrack {{2{J_{2}\left( \varphi_{m} \right)}{\cos \left( {4\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack}} +}} \\ {{p_{1}{{\sin \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}\left\lbrack {{2{J_{1}\left( \varphi_{m} \right)}{\cos \left( {2\pi \; f_{m}t} \right)}} + {2{J_{3}\left( \varphi_{m} \right)}{\cos \left( {6\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack}}} \\ {= {p_{1}{\cos \left\lbrack {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}} + {\varphi_{m}{\cos \left( {2\pi \; f_{m}t} \right)}}} \right\rbrack}}} \end{matrix} & (9) \end{matrix}$

Each component in (9), without regard to amplitude variations, only consider the frequency distribution, 2p₁J_(N)(Φ_(m)) cos (Φ₀₁+ΔΦ₁(t)) cos (2Nπf_(m)t) (N=1,3,5, . . . ) is move frequency spectrum of 2p₁J_(N)(Φ_(m)) cos (Φ₀₁+ΔΦ₁(t)) from 0 frequency to Nf_(m); 2p₁J_(M) (Φ_(m)) sin (Φ₀₁+ΔΦ₁(t)) cos (2Mπf_(m)t) (M=2,4,6, . . . ) is move frequency spectrum of 2p₁J_(N) (Φ_(m2)) sin (Φ₀₁+ΔΦ₁ (t)) from 0 frequency to Mf_(m). The frequency component of P_(B) is near 0 frequency. Suppose f_(s1max) is the max frequency of sin (Φ₀₁+ΔΦ₁ (t)) (or cos (Φ₀₁+ΔΦ₁ (t))), f_(sBmax) is the max frequency of P_(B), then f_(m) can be:

f _(m) >f _(sBmax) +f _(s1max)   (10)

that is, f_(m), is large enough to make the spectral of P_(B) and P do not overlap, then use the high-pass filter to filter out P_(B) to get a complete signal P with no interference. This may separate interference signal caused by scattering point from the reflected light formed by arriving the feedback device. After obtaining signal P, further use phase reconstruct method commonly used in interference structure, the restore signal can be obtained:

ΔΦ(t)=ΔΦ₁(t)+Φ_(m)cos(2πf _(m) t)   (11)

It can be seen that while satisfying the formula (8) and f_(m) is located out of the frequency component of ΔΦ₁(t), use the filtering technology to filter out frequency components of f_(m), then obtain ΔΦ₁ (t) to demodulate the signal.

The interference structure has two interference output ports, the interference signals of the two ports are expressed as:

$\begin{matrix} {P_{3a\; 2} = {{p_{1}{\cos \left\lbrack {\varphi_{11} + {\Delta \; {\varphi_{1}(t)}} + {{\Delta\varphi}_{c}(t)}} \right\rbrack}} + {\sum\limits_{i}{p_{Bi}{\cos \left\lbrack {\varphi_{{3a\; 2} - {B\; 0\; i}} + {\Delta \; {\varphi_{B\; 1i}(t)}}} \right\rbrack}}}}} & (12) \\ {P_{3a\; 3} = {{p_{1}{\cos \left\lbrack {\varphi_{12} + {\Delta \; {\varphi_{1}(t)}} + {{\Delta\varphi}_{c}(t)}} \right\rbrack}} + {\sum\limits_{i}{p_{Bi}{\cos \left\lbrack {\varphi_{{3a\; 3} - {B\; 0\; i}} + {\Delta \; {\varphi_{B\; 1i}(t)}}} \right\rbrack}}}}} & (13) \end{matrix}$

Φ₁₁ and Φ₁₂ are an initial phase corresponding to the interference output of the two ports, and φ₁₁−φ₁₂≠nπ, n; is an integer.

According to the method previously described in the present invention, we can be obtained two signals with a fixed phase difference:

P _(3a2) =p ₁cos[Φ₁₁+ΔΦ₁(t)+Φ_(m)cos(2πf _(m) t)]  (14)

P _(3a3) =p ₁cos[Φ₁₂+ΔΦ₁(t)+Φ_(m)cos(2πf _(m) t)]  (15)

According to formula (14) and formula (15), signal ΔΦ(t) can be restored, and use the filtering technology to filter out frequency components of f_(m), then obtain signal ΔΦ₁(t).

According to the above description, the specific steps of the inventive method are summarized as follows:

1) concatenating phase modulator 9 in the tail of a single core feedback sensing fiber;

2) Selecting signal frequency f_(m) loaded in phase modulator 9, f_(m) satisfy the following conditions:

f_(m)>f_(sBmax)+f_(s1max), and f_(m) is located out of the frequency component of ΔΦ₁ (t);

3) applying a sinusoidal signal at the phase modulator, the carrier generated by the modulated signal is expressed as:

ΔΦ_(c)(t)=Φ_(m)cos(2πf _(m) t);

4) adjusting the amplitude of the sinusoidal signal, so that:

J ₀(Φ_(m))=0,

an frequency component of the effective interference signal formed by feedback device 2 distributes at the sideband of the fundamental frequency and multiple frequency carrier frequency f_(m), frequency components are not in the vicinity of zero frequency, effective interference signal P is expressed as:

$\begin{matrix} {P = {0 + {p_{1}{{\cos \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}\left\lbrack {{2{J_{2}\left( \varphi_{m} \right)}{\cos \left( {4\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack}} +}} \\ {{p_{1}{{\sin \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}\left\lbrack {{2{J_{1}\left( \varphi_{m} \right)}{\cos \left( {2\pi \; f_{m}t} \right)}} + {2{J_{3}\left( \varphi_{m} \right)}{\cos \left( {6\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack}}} \\ {= {p_{1}{\cos \left\lbrack {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}} + {\varphi_{m}{\cos \left( {2\pi \; f_{m}t} \right)}}} \right\rbrack}}} \end{matrix}$

At this time, only interfering signal P_(B) formed by backscattered/backreflected light's interference is in the vicinity of zero frequency;

5) high-pass filtering P_(alt) to filter out the interference signal P_(B) and remain effective signal P, separating interference signal with effective signal to get effective signal; and

6) using effective signal P to further reconstruct signal ΔΦ(t):

ΔΦ(t)=ΔΦ₁(t)+Φ_(m)cos(2πf _(m) t)

Advantage of the present invention is that it can effectively eliminate the impact of backscattered(reflected) light in single core optical fiber sensing light path, the useful information is extracted from the signal of serious disturbances, which significantly improves the measurement of distance, enhance adaptability to the line of interference measurement system. The technology uses a unique carrier signal loading and demodulating method, no need to provided a reference signal homologous with carry signal at signal demodulation side like the conventional PGC demodulation method. Therefore, in the long-distance monitoring, easier to monitor end of the cable extending freely. Meanwhile, the technology requires no reference signal, structure of this method is simple and easier to implement.

Distributed optical fiber line monitoring system of the invention can be widely used in long distance monitoring of safety monitoring in the field of telecommunications lines, power transmission lines, gas pipelines, oil pipelines, border; also be used for safety monitoring of large buildings such as dams, tunnels, mines, etc.

BRIEF DESCRIPTION OF FIGURES

FIG. 1 is a positioning schematic diagram of single core feedback sensor;

FIG. 2 is a diagram of single core feedback interference structure;

FIG. 3 is a spectrum of the phase signal demodulated from interference signal, “O” is frequency “notch point.”;

FIG. 4 is a schematic diagram of impact by backscattered light;

FIG. 5 is a diagram of light path connection method which use phase generated carrier technology to eliminate the impact of backscattered;

FIGS. 6 is a concrete construction which the method of the present invention may be implemented.

REFERENCE NUMERAL

1: end of the sensing optical fiber 6, 2: feedback device, 3: for the N * M (N, M are integers) coupler, 4: P * Q (P, Q are integers) coupler, 5: optical fiber delayer, delay τ, 6: sensor optical fiber (optical cable) and feedback device 2 constituted, 3 a 1, 3 a 2, . . . , 3 aN, 3 b 1, 3 b 2: port of coupler 3, 3 a 1, 3 a 2, . . . , 3 aN: co-rotating ports with a total of N, 3 b 1, 3 b 2: two ports in another group co-rotating ports (with a total of M) of coupler 3. 4 a 1, 4 a 2, 4 b 1: ports of coupler 4, 4 a 1, 4 a 2: two ports in a group co-rotating ports (with a total of P) of coupler 4, 4 b 1: two ports in another group co-rotating ports (with a total of Q) of coupler 4. 7, 8: scattering point in optical fiber, 9: phase modulator.

Embodiment

The measurement system of the embodiment use interference structure shown in FIG. 3. Length of sensing optical cable 6 is 30 km. Light source is S03-B type super super radiation diode (SLD) produced by 44 research institute of the Institute of Industrial Electronics Group Corporation, with the operating wavelength of 1310 nm. Coupler 3 uses average of 3 *3 Optical Fiber tapered single mode coupler. Coupler 4 uses average of 2 * 2 Optical Fiber tapered single mode Coupler. Both of them are produced by Wuhan Research Institute of Posts and Telecommunications. Fiber used by fiber delayer is G652 single-mode fiber. Photoelectric converter used in photoelectric conversion and information processing is GT322C500 of InGaAs photodetector produced by 44 research institute. Feedback device 2 is produced by optical fiber end steamed aluminized production, reflectance greater than 95%. Phase modulator 9 concatenating at the tail end is produced by winding optical fiber on a piezoelectric ceramic made. Interference signal baseband bandwidth <10 kHz, frequency of sinusoidal signal loaded at phase modulator is 60 kHz.

In the single core sensing path, an active joint connection point is 10 km from end of sensing optical cable 6 (feedback device 2), at which point reflection>2 dB, disturbance applied near the port 4 b 1 to sensor cable 6. If do not use this The method of the invention, the system can not properly positioned. After use the modulation and demodulation method, the system can locate accurately.

FIG. 6 is a concrete construction which the method of the present invention may be implemented. In this configuration, the coupler 3 is coupled using average 3 * 3 device, light input to port 3 a 1, two interference signals output from two ports 3 a 3 and 3 a 2, these two interference signals can be represented as:

$\begin{matrix} {P_{3a\; 2} = {{p_{1}{\cos \left\lbrack {\frac{2\pi}{3} + {\Delta \; {\varphi_{1}(t)}} + {\Delta \; {\varphi_{c}(t)}}} \right\rbrack}} + {\sum\limits_{i}{p_{Bi}{\cos \left\lbrack {\varphi_{{3\; a\; 2} - {{B0}\; i}} + {\Delta \; {\varphi_{B\; 1i}(t)}}} \right\rbrack}}}}} & (16) \\ {P_{3a\; 3} = {{p_{1}{\cos \left\lbrack {{- \frac{2\pi}{3}} + {\Delta \; {\varphi_{1}(t)}} + {\Delta \; {\varphi_{c}(t)}}} \right\rbrack}} + {\sum\limits_{i}{p_{Bi}{\cos \left\lbrack {\varphi_{{3\; a\; 2} - {{B0}\; i}} + {\Delta \; {\varphi_{B\; 1i}(t)}}} \right\rbrack}}}}} & (17) \end{matrix}$

Suppose the max frequency of ΔΦ₁(t)) is f_(sΦmax), then:

f _(m) >f _(sBmax) +f _(s1max) f _(m) >f _(sΦmax)   (18)

according to the method described above, the phase modulation amplitude set so as to satisfy equation (7), high-pass filter interference signal to filter out stray light caused by interference, will receive the following signals:

$\begin{matrix} {P_{3a\; 2} = {p_{1}{\cos \left\lbrack {\frac{2\pi}{3} + {\Delta \; {\varphi_{1}(t)}} + {\varphi_{m}{\cos \left( {2\pi \; f_{m}t} \right)}}} \right\rbrack}}} & (19) \\ {P_{3a\; 3} = {p_{1}{\cos \left\lbrack {{- \frac{2\pi}{3}} + {\Delta \; {\varphi_{1}(t)}} + {\varphi_{m}{\cos \left( {2\pi \; f_{m}t} \right)}}} \right\rbrack}}} & (20) \end{matrix}$

then, use formula (19) and formula (20), signal ΔΦ(t) can be restored (Reference: Wu Hongyan, etc; fiber interference positioning system based signal demodulation technique [J]; sensors and micro systems, 2007, 26 (5): p45-51):

ΔΦ(t)=Δ₁(t)+Φ_(m)cos(2πf _(m) t)   (16)

Low-pass filter ΔΦ(t), we can obtain ΔΦ₁ (t). 

1. A method for reducing interference from scattered light of interference path by generating carrier through phase, characterized by comprising the following steps: (1) concatenating phase modulator in the tail of a single core feedback sensing fiber, phase modulator introduce the interferometer phase difference ΔΦ_(c) (t), after reaching feedback means through the phase modulator, the light reflect to the optical cable and occurs interference signal, the signal is expressed as: P=p ₁cos[Φ₀+ΔΦ₁(t)+ΔΦ_(c)(t)]  (1) wherein, p₁ is a constant coefficient related to the system parameters, Φ₀ is an initial phase of the interference structures and a constant, ΔΦ₁ (t) is an interference phase difference caused by disturbance ; as to the back scattered light caused by previous path in the phase modulator in optical fable, changes in the phase are not affected by the signal applied to the phase modulator, part of the optical interference signal is expressed as: $\begin{matrix} {P_{B} = {\sum\limits_{i}{p_{Bi}{\cos \left\lbrack {\varphi_{B\; 0i} + {\Delta \; {\varphi_{B\; 1i}(t)}}} \right\rbrack}}}} & (2) \end{matrix}$ wherein, p_(Bi) is an interference coefficient caused by the i-th scattering point of the optical fiber, Φ _(B 0 i) is an initial phase corresponding to the i-th scattering point, ΔΦ_(B1i) (t) is an interference phase difference corresponding to the i-th scattering point and caused by disturbance, $\sum\limits_{i}.$ represented the sum of all the scattered points along the previous induction fiber of phase modulator ; thus, the total output signal change portion indicates as follows: P _(alt) =P+P _(B)   (3) J_(n) order Bessel function expansion of Formula (1) is expressed as: $\begin{matrix} {\begin{matrix} {P = {p_{1}{\cos \left\lbrack {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}} + {\varphi_{m}{\cos \left( {2\pi \; f_{m}} \right)}}} \right\rbrack}}} \\ {= {p_{1}{\cos \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}}} \\ {{\left\lbrack {{J_{0}\left( \varphi_{m} \right)} + {2{J_{2}\left( \varphi_{m} \right)}{\cos \left( {4\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack +}} \\ {{p_{1}{\sin \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}}} \\ {\left\lbrack {{2{J_{1}\left( \varphi_{m} \right)}{\cos \left( {2\pi \; f_{m}t} \right)}} + {2{J_{3}\left( \varphi_{m} \right)}{\cos \left( {6\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack} \end{matrix}{and}} & (5) \\ \begin{matrix} {P_{alt} = {P + P_{B}}} \\ {= {P_{B} + {p_{1}{\cos \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}}}} \\ {{\left\lbrack {{J_{0}\left( \varphi_{m} \right)} + {2{J_{2}\left( \varphi_{m} \right)}{\cos \left( {4\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack +}} \\ {{p_{1}{\sin \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}}} \\ {\left\lbrack {{2{J_{1}\left( \varphi_{m} \right)}{\cos \left( {2\pi \; f_{m}t} \right)}} + {2{J_{3}\left( \varphi_{m} \right)}{\cos \left( {6\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack} \\ {= {\left\lbrack {P_{B} + {p_{1}{{\cos \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)} \cdot {J_{0}\left( \varphi_{m} \right)}}}} \right\rbrack +}} \\ {{p_{1}{\cos \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}}} \\ {\left\lbrack {{2{J_{2}\left( \varphi_{m} \right)}{\cos \left( {4\pi \; f_{m}t} \right)}} + \ldots}\; \right\rbrack} \\ {{p_{1}{\sin \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}}} \\ {\left\lbrack {{2{J_{1}\left( \varphi_{m} \right)}{\cos \left( {2\pi \; f_{m}t} \right)}} + {2{J_{3}\left( \varphi_{m} \right)}{\cos \left( {6\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack} \end{matrix} & (6) \end{matrix}$ (2) Selecting signal frequency f_(m) loaded in phase modulator, f_(m), satisfy the following conditions: f_(m)>f_(sBmax)+f_(s1max), and f_(m) is located out of the frequency component of ΔΦ₁ (t); f_(s1max) is the maximum frequency of sin (Φ₀₁+ΔΦ₁ (t)) or cos (Φ₀₁+ΔΦ₁ (t)), f_(sBmax) is the maximum frequency of P_(B); (3) applying a sinusoidal signal at the phase modulator, the carrier generated by the modulated signal is expressed as: ΔΦ_(c)(t)=Φ_(m)cos(2πf _(m) t), Φ_(m) is the amplitude of Δ Φ _(c) (t); (4) adjusting the amplitude of the sinusoidal signal, so that: J ₀(Φ_(m))=0, an frequency component of the effective interference signal formed by feedback means distributes at the sideband of the fundamental frequency and multiple frequency carrier frequency f_(m), frequency components are not in the vicinity of zero frequency, effective interference signal P is expressed as: $\begin{matrix} {P = {0 + {p_{1}{\cos \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}}}} \\ {{\left\lbrack {{2{J_{2}\left( \varphi_{m} \right)}{\cos \left( {4\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack +}} \\ {{p_{1}{\sin \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}}} \\ {\left\lbrack {{2{J_{1}\left( \varphi_{m} \right)}{\cos \left( {2\pi \; f_{m}t} \right)}} + {2{J_{3}\left( \varphi_{m} \right)}{\cos \left( {6\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack} \\ {= {p_{1}{\cos \left\lbrack {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}} + {\varphi_{m}{\cos \left( {2\pi \; f_{m}t} \right)}}} \right\rbrack}}} \end{matrix}$ At this time, only interfering signal P_(B) formed by backscattered light's interference is in the vicinity of zero frequency; (5) high-pass filtering P_(alt) to filter out the interference signal P_(B) and remain effective signal P, separating interference signal with effective signal to get effective signal.
 2. The method according to claim 1, wherein, using effective signal P to further reconstruct signal ΔΦ(t): ΔΦ(t)=ΔΦ₁(t)+Φ_(m)cos(2πf _(m) t) filtering ΔΦ(t) to filter out Φ_(m) cos(2πf_(m)t) to obtain a interference phase difference signal ΔΦ₁(t) caused by the disturbance.
 3. The method according to claim 1, wherein the interference structure provided with two interference output ports, the two-way interference signals are expressed as: $P_{3a\; 2} = {{p_{1}{\cos \left\lbrack {\varphi_{11} + {\Delta \; {\varphi_{1}(t)}} + {\Delta \; {\varphi_{c}(t)}}} \right\rbrack}} + {\sum\limits_{i}{p_{Bi}{\cos \left\lbrack {\varphi_{{3a\; 2} - {{B0}\; i}} + {\Delta \; {\varphi_{B\; 1i}(t)}}} \right\rbrack}}}}$ $P_{3a\; 3} = {{p_{1}{\cos \left\lbrack {\varphi_{12} + {\Delta \; {\varphi_{1}(t)}} + {\Delta \; {\varphi_{c}(t)}}} \right\rbrack}} + {\sum\limits_{i}{p_{Bi}{\cos \left\lbrack {\varphi_{{3a\; 3} - {{B0}\; i}} + {\Delta \; {\varphi_{B\; 1i}(t)}}} \right\rbrack}}}}$ and φ₁₁−φ₁₂≠nπ, n; is an integer obtaining two signals having a fixed phase difference: P _(3a2) =p ₁cos[Φ₁₁+ΔΦ₁(t)+Φ_(m)cos(2πf _(m) t)] P _(3a3) =p ₁cos[Φ₁₂+ΔΦ₁(t)+Φ_(m)cos(2πf _(m) t)] combining the two signals to recover the signal ΔΦ(t)=ΔΦ₁(t)+Φ_(m)cos(2πf_(m)t).
 4. The method according to claim 1, wherein, the signal frequency on the loading phase modulator f_(m)>f_(sΦmax), low-pass filtering the signal ΔΦ(t)=ΔΦ₁(t)+Φ_(m)cos(2πf_(m)t) to filter out frequency components of f_(m) to obtain a interference phase difference signal caused by the disturbance.
 5. A method for reducing interference from scattered light of interference path by generating carrier through phase, characterized by comprising the following steps: concatenating phase modulator in the tail of a single core feedback sensing fiber; selecting sinusoidal modulating signal frequency loaded in phase modulator, so that change part of the total output signal includes interference signals and effective interference signals, and spectrums of the interference signal and spectrums of the effective interference signals do not overlap, and the frequency of the sinusoidal modulation signal is located outside the frequency component of interference phase difference caused by the disturbance; applying the sinusoidal modulation signal to the phase modulator to generate carrier; adjusting the amplitude of the carrier so that the value of the J₀ order Bessel function at this amplitude is equal to zero; and high-pass filtering the change portion of the total output signal to filter out the interference signal and remain the effective interference signal.
 6. A method according to claim 5, wherein further comprising the following step: reconstructing the remained effective interference signal to obtain reconstruction signal, and then removing the frequency component of the sinusoidal modulation signal from the reduction signal to obtain a interference phase difference signal caused by the disturbance.
 7. A method according to claim 6, wherein, multi-path interference signals output from a plurality of output ports are jointed to reconstructing the phase.
 8. A method according to claim 6, wherein, Low-pass filtering the reconstruction signal to filter out frequency component of the sinusoidal modulation signal.
 9. A method according to claim 7, wherein, two-path interference signals output from two output ports are jointed to reconstructing the phase.
 10. A system for reducing interference from scattered light of interference path by generating carrier through phase, characterized by comprising: phase modulator which is concatenated in the tail of a single core feedback sensing fiber; frequency selector which is used to select sinusoidal modulating signal frequency loaded in phase modulator, so that change part of the total output signal includes interference signals and effective interference signals, and spectrums of the interference signal and spectrums of the effective interference signals do not overlap, and the frequency of the sinusoidal modulation signal is located outside the frequency component of interference phase difference caused by the disturbance; frequency applicator which is used to apply the sinusoidal modulation signal to the phase modulator to generate carrier; carrier regulator which is used to adjust the amplitude of the carrier so that the value of the J₀ order Bessel function at this amplitude is equal to zero; and Signal remain device which is used to high-pass filter the change portion of the total output signal to filter out the interference signal and remain the effective interference signal.
 11. A method for reducing interference from scattered light of interference path by generating carrier through phase, characterized by comprising the following steps: 1) concatenating phase modulator (9) in the tail of a single core feedback sensing fiber; 2) Selecting signal frequency f_(m) loaded in phase modulator (9), f_(m) satisfy the following conditions: f_(m)>f_(sBmax)+f_(s1max), and f_(m) is located out of the frequency component of ΔΦ₁ (t); 3) applying a sinusoidal signal at the phase modulator, the carrier generated by the modulated signal is expressed as: ΔΦ_(c)(t)=Φ_(m)cos(2πf_(m)t); 4) adjusting the amplitude of the sinusoidal signal, so that: J ₀(Φ_(m))=0, an frequency component of the effective interference signal formed by feedback device (2) distributes at the sideband of the fundamental frequency and multiple frequency carrier frequency f_(m), frequency components are not in the vicinity of zero frequency, effective interference signal P is expressed as: $\begin{matrix} {P = {0 + {p_{1}{\cos \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}}}} \\ {{\left\lbrack {{2{J_{2}\left( \varphi_{m} \right)}{\cos \left( {4\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack +}} \\ {{p_{1}{\sin \left( {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}}} \right)}}} \\ {\left\lbrack {{2{J_{1}\left( \varphi_{m} \right)}{\cos \left( {2\pi \; f_{m}t} \right)}} + {2{J_{3}\left( \varphi_{m} \right)}{\cos \left( {6\pi \; f_{m}t} \right)}} + \ldots} \right\rbrack} \\ {= {p_{1}{\cos \left\lbrack {\varphi_{0} + {\Delta \; {\varphi_{1}(t)}} + {\varphi_{m}{\cos \left( {2\pi \; f_{m}t} \right)}}} \right\rbrack}}} \end{matrix}$ At this time, only interfering signal P_(B) formed by backscattered/backreflected light's interference is in the vicinity of zero frequency; 5) high-pass filtering P_(alt) to filter out the interference signal P_(B) and remain effective signal P, separating interference signal with effective signal to get effective signal; and 6) using effective signal P to further reconstruct signal ΔΦ(t): ΔΦ(t)=ΔΦ₁(t)+Φ_(m)cos(2πf _(m) t) filtering ΔΦ(t) to filter out Φ_(m) cos(2πf_(m)t) to obtain a interference phase difference signal ΔΦ₁ (t) caused by the disturbance. 